Page 81 - Kaleidoscope Academic Conference Proceedings 2021
P. 81

Connecting physical and virtual worlds




           and generally has a good performance. In this section, the  phase rotation of the QL terms in Equation (8). The FFT size
           receiver is briefly described and analyzed to demonstrate the  should be large enough to ensure the coherent combination
           basic idea to design an NPRACH receiver. Without a special  of the QL terms. Suppose the coherent combination needs
           statement, in the following paragraphs the reference method  the phase rotation to be less than π/2, it gives a lower bound
           means the receiver in [8].                         on the S f , i.e.,
           An NPRACH preamble consists of LM single-subcarrier
           OFDM symbols. Without AWGN, the received data in the
           LM subcarriers is as follows.                                          2Q(N CP + LN)
                                                                                                           (10)
                                                                             S f >             .
                                             sin(π∆ f )                                N
                              jπ∆f (N−1−2D)/N
             Y m,l (Ω(m)) =h(m, l)e
                                           N sin(π∆ f /N)
                        × e j2π∆f (m(N C P +LN)+lN)/N −j2πDΩ(m)/N  ,  Because the NPRACH preamble has a long duration but only
                                              e
                                                         (6)  locates in a few subcarriers, the phase rotation caused by
                          m = 0, . . ., M − 1; l = 0, . . ., L − 1.
                                                              small S D is relatively small.
           Assume the channel coefficient h(m, l) is consistent in the
           period of the NPRACH preamble, then the variation of phases  When the Doppler in the uplink channel increases, the
           of the ML complex numbers in Equation (6) is determined by  term sin(π∆ f )/sin(π∆ f /N) in Equation (6) will decrease.
           the TO and FO. Given an assumption on TO and FO, the BS  The correlation peak in Equation (7) will decrease as well.
           is able to construct a local sequence with the corresponding  Meanwhile, the leaked power from other preambles may form
           phase variation and correlate with the received ML numbers.  another peak in the correlation. The NPRACH detection
           When the assumption is near the real TO and FO, the BS can  performance will be largely degraded.
           get the correlation peak.
           Based on the phase rotation presented in Equation (6), a two
           dimensional FFT receiver for NPRACH was proposed in [8],  3.2 Proposed Method
           in which the TO and FO is jointly estimated. Assume in
           every Q symbol groups the channel coefficient h(m, l) can  Due to the impact of FO, the power of the received preamble
           be regarded as consistent, and L/Q is an integer. Then the  will leak into the adjacent subcarriers.  As presented in
           correlation is defined as                           Equation (5), the received power in the k-th subcarriers is
                                                              mainly determined by sin(π(Ω(m) + ∆ f − k))/sin(π(Ω(m) +
                                L/Q−1                         ∆ f − k)/N). Assume Ω(m) = 6 and N = 1024, the received
                                                2
                                 Õ
                      J(D, ∆ f ) =     J g (D, ∆ f ) ,   (7)  power in different subcarriers is shown in Figure 2. The figure

                                                              shows that with the increase of FO from 0 to 0.5, the miss
                                 g=0
           where                                              detection rate of the preamble and its interference to adjacent
                                                              preambles will both increase.
                      (g+1)Q−1 L−1
                        Õ    Õ
            J g (D, ∆ f ) =     Y m,l (Ω(m))
                       m=gQ  l=0
                                             e
                      × e −j2π∆f (m(N C P +LN)+lN)/N j2πDΩ(m)/N  . (8)
           The TO and FO are jointly estimated as the pair (D, ∆ f ) which
           maximizes the correlation value in Equation (7).
           The search for the best (D, ∆ f ) can be effectively solved
           by two dimensional FFT. Actually, the Equation (8) can be
           rewritten as

             (g+1)Q−1     L−1            !              !
               Õ      Õ            −j2π∆f l  −j2π∆f m  N C P +L N
                         Y m,l (Ω(m))e    e         N
              m=gQ    l=0
                         j2πΩ(m)  D
                      × e      N .                       (9)
           By applying FFT, the J g (D, ∆ f ) can be evaluated in the range  Figure 2 – The received power in different subcarriers
           D ∈ [0, N CP ) and the normalized frequency offset ∆ f ∈
           (−0.5, 0.5). The FFT size determines the granularity of the  In this subsection, a new receiver is proposed to solve the
           search for the optimal (D, ∆ f ). Obviously, the increase of  performance degradation caused by a large FO. The basic
           FFT size will improve the computational complexity, but the  idea is to make an estimation based on not only the Ω(m)-th
           decrease of FFT size may lead to a large estimation error. Let  subcarrier, but also the adjacent subcarriers. In each OFDM
           S D and S f denote the FFT sizes for D and ∆ f , respectively.  symbol, the received data in three subcarriers are coherently
           Then the smallest distance between the evaluated ∆ f and the  combined to reduce the miss detection rate and FO/TO
           real normalized FO is up to 0.5/S f , which will cause the  estimation error. According to the Equation (5), the received




                                                           – 19 –
   76   77   78   79   80   81   82   83   84   85   86